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LTC1046 "Inductorless" 5V to - 5V Converter
FEATURES
s s s s s s
DESCRIPTIO
s s s s
50mA Output Current Plug-In Compatible with ICL7660/LTC1044 ROUT = 35 Maximum 300A Maximum No Load Supply Current at 5V Boost Pin (Pin 1) for Higher Switching Frequency 97% Minimum Open-Circuit Voltage Conversion Efficiency 95% Minimum Power Conversion Efficiency Wide Operating Supply Voltage Range: 1.5V to 6V Easy to Use Low Cost
The LTC(R)1046 is a 50mA monolithic CMOS switched capacitor voltage converter. It plugs in for ICL7660/ LTC1044 in 5V applications where more output current is needed. The device is optimized to provide high current capability for input voltages of 6V or less. It trades off operating voltage to get higher output current. The LTC1046 provides several voltage conversion functions: the input voltage can be inverted (VOUT = - VIN), divided (VOUT =VIN/2) or multiplied (VOUT = nVIN). Designed to be pin-for-pin and functionally compatible with the ICL7660 and LTC1044, the LTC1046 provides 2.5 times the output drive capability.
, LTC and LT are registered trademarks of Linear Technology Corporation.
APPLICATIO S
s s s
Conversion of 5V to 5V Supplies Precise Voltage Division, VOUT = VIN /2 Supply Splitter, VOUT = VS /2
TYPICAL APPLICATIO
Output Voltage vs Load Current for V + = 5V
-5
Generating - 5V from 5V
-4
OUTPUT VOLTAGE (V)
LTC1046 1 2 BOOST CAP + GND CAP - V+ OSC LV VOUT 8 7 6 5 -5V INPUT 10F 5V INPUT
-3
ICL7660/LTC1044, ROUT = 55 LTC1046, ROUT = 27
+
10F
3 4
-2
-1
1046 TA01
0 0 10 20 30 40 LOAD CURRENT, IL (mA) 50
1046 TA02
U
TA = 25C
+
U
U
1
LTC1046 ABSOLUTE
(Note 1)
AXI U
RATI GS
PACKAGE/ORDER I FOR ATIO
TOP VIEW BOOST 1 CAP + 2 GND 3 CAP - 4 J8 PACKAGE 8-LEAD CERDIP 8 7 6 5 V+ OSC LV VOUT
Supply Voltage ....................................................... 6.5V Input Voltage on Pins 1, 6 and 7 (Note 2) ............................ - 0.3 < VIN < (V +) + 0.3V Current into Pin 6 .................................................. 20A Output Short Circuit Duration (V + 6V) ............................................... Continuous Operating Temperature Range LTC1046C .................................... 0C TA 70C LTC1046I ................................. - 40C TA 85C LTC1046M .................................... - 55C to 125C Storage Temperature Range ............... - 65C to + 150C Lead Temperature (Soldering, 10 sec.)................. 300C
ORDER PART NUMBER LTC1046CN8 LTC1046CS8 LTC1046IN8 LTC1046IS8 LTC1046MJ8 S8 PART MARKING 1046 1046I
N8 PACKAGE 8-LEAD PDIP
S8 PACKAGE 8-LEAD PLASTIC SO TJMAX = 160C, JA = 100C (J8) TJMAX = 110C, JA = 130C (N8) TJMAX = 150C, JA = 150C (S8)
The q denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. V + = 5V, COSC = 0pF, unless otherwise noted.
SYMBOL PARAMETER IS Supply Current CONDITIONS RL = , Pins 1 and 7 No Connection RL = , Pins 1 and 7 No Connection, V+ = 3V RL = 5k RL = 5k V+ = 5V, IL = 50mA (Note 3) V+ = 2V, IL = 10mA fOSC PEFF VOUTEFF IOSC Oscillator Frequency Power Efficiency Voltage Conversion Efficiency Oscillator Sink or Source Current V+ = 5V (Note 4) V+ = 2V RL = 2.4k RL = VOSC = 0V or V+ Pin 1 = 0V Pin 1 = V+
q q q q
ELECTRICAL CHARACTERISTICS
MIN
LTC1046C TYP MAX 165 35 300
MIN
LTC1046I/M TYP MAX 165 35 300
UNITS A A V
V+L V+H ROUT
Minimum Supply Voltage Maximum Supply Voltage Output Resistance
1.5 6 27 27 60 20 4 95 97 30 5.5 97 99.9 35 45 85
1.5 6 27 27 60 20 4 95 97 30 5.5 97 99.9 35 50 90
q q
4.2 15
35 45
4.2 15
40 50
Note 1: Absolute Maximum Ratings are those values beyond which the life of the device may be impaired. Note 2: Connecting any input terminal to voltages greater than V+ or less than ground may cause destructive latch-up. It is recommended that no inputs from sources operating from external supplies be applied prior to power-up of the LTC1046.
Note 3: ROUT is measured at TJ = 25C immediately after power-on. Note 4: fOSC is tested with COSC = 100pF to minimize the effects of test fixture capacitance loading. The 0pF frequency is correlated to this 100pF test point, and is intended to simulate the capacitance at pin 7 when the device is plugged into a test socket and no external capacitor is used.
2
U
V kHz kHz % % A A
W
U
U
WW
W
LTC1046 TYPICAL PERFOR A CE CHARACTERISTICS
Output Resistance vs Oscillator Frequency
500 TA = 25C V + = 5V IL = 10mA
1000
OUTPUT RESISTANCE, RO ()
OUTPUT RESISTANCE, RO ()
400
OUTPUT RESISTANCE ()
300 C1 = C2 = 10F
C1 = C2 = 1F C1 = C2 = 100F
200
100
0 100
1k
10k
OSCILLATOR FREQUENCY, fOSC (Hz)
1046 G01
Power Conversion Efficiency vs Load Current for V+ = 2V
POWER CONVERSION EFFICIENCY, PEFF (%) POWER CONVERSION EFFICIENCY, PEFF (%) 100 90 80 70 60 50 40 30 20 10 0 0 1 2 TA = 25C V + = 2V C1 = C2 = 10F fOSC = 8kHz 345678 LOAD CURRENT, IL (mA) 9 10 IS PEFF 10 9 8 SUPPLY CURRENT (mA) 7 6 5 4 3 2 1 0 100 90 80 70 60 50 40 30 20 10 0
POWER CONVERSION EFFICIENCY, PEFF (%)
Output Voltage vs Load Current for V+ = 2V
2.5 TA = 25C 2.0 V + = 2V fOSC = 8kHz 1.5 C1 = C2 = 10F 1.0 0.5 0.0 -0.5 -1.0 -1.5 -2.0 -2.5 0 2 4 6 8 10 12 14 16 18 20 LOAD CURRENT, IL (mA)
1046 G07
3
OSCILLATOR FREQUENCY, fOSC (kHz)
OUTPUT VOLTAGE (V)
OUTPUT VOLTAGE (V)
SLOPE = 52 -4 -5 0 10 20 30 40 50 60 70 80 90 100 LOAD CURRENT, IL (mA)
1046 G08
UW
1046 G04
(Using Test Circuit in Figure 1) Output Resistance vs Temperature
80 70 60 50 40 30 20 V + = 5V, COSC = 0pF V + = 2V, COSC = 0pF C1 = C2 = 10F
Output Resistance vs Supply Voltage
TA = 25C IL = 3mA
100
COSC = 100pF
COSC = 0pF
100k
10 0 1 2 3 4 5 6 7 SUPPLY VOLTAGE, V + (V)
1046 G02
10 -55
-25 0 75 100 25 50 AMBIENT TEMPERATURE (C)
125
1046 G03
Power Conversion Efficiency vs Load Current for V+ = 5V
100 PEFF 90 80 SUPPLY CURRENT (mA) 70 60 50 IS 40 30 TA = 25C V + = 5V C1 = C2 = 10F fOSC = 30kHz 0 10 20 50 30 40 LOAD CURRENT, IL (mA) 60 70 20 10 0
100 98 96 94 92 90 88 86 84 82
Power Conversion Efficiency vs Oscillator Frequency
A A = 100F, 1mA B = 100F, 15mA C = 10F, 1mA D = 10F, 15mA E = 1F, 1mA F = 1F, 15mA B E V + = 5V TA = 25C C1 = C2
C
D F
80 100
1k 10k 100k OSCILLATOR FREQUENCY, fOSC (Hz)
1M
1046 G05
1046 G06
Output Voltage vs Load Current for V+ = 5V
5 4
100
Oscillator Frequency as a Function of COSC
V + = 5V TA = 25C PIN 1 = V + 10
TA = 25C V + = 5V fOSC = 30kHz C1 = C2 = 10F
2 1 0 -1 -2 -3 SLOPE = 27
PIN 1 = OPEN 1
0.1 10 100 10000 1000 1 EXTERNAL CAPACITOR (PIN 7 TO GND), COSC (pF)
1046 G09
3
LTC1046 TYPICAL PERFOR A CE CHARACTERISTICS
Oscillator Frequency as a Function of Supply Voltage
100 TA = 25C COSC = 0pF
OSCILLATOR FREQUENCY, fOSC (kHz)
OSCILLATOR FREQUENCY, fOSC (kHz)
10
1 0 1 2 3 6 4 5 AMBIENT TEMPERATURE (C) 7
TEST CIRCUIT
LTC1046 1 2 BOOST CAP + GND CAP - V+ OSC LV VOUT 8 7 6 5 COSC EXTERNAL OSCILLATOR
Figure 1
APPLICATI
S I FOR ATIO
Theory of Operation To understand the theory of operation of the LTC1046, a review of a basic switched capacitor building block is helpful. In Figure 2, when the switch is in the left position, capacitor C1 will charge to voltage V1. The total charge on C1 will be q1 = C1V1. The switch then moves to the right, discharging C1 to voltage V2. After this discharge time, the charge on C1 is q2 = C1V2. Note that charge has been transferred from the source, V1, to the output, V2. The amount of charge transferred is: q = q1 - q2 = C1(V1 - V2).
If the switch is cycled "f" times per second, the charge transfer per unit time (i.e., current) is: I = f * q = f * C1(V1 - V2).
V1 f RL C1 C2
1046 F02
Figure 2. Switched Capacitor Building Block
4
+
U
W
UW
+ C1
10F
(Using Test Circuit in Figure 1) Oscillator Frequency vs Temperature
40 38 36 34 32 30 28 26 -55 V + = 5V COSC = 0pF
-25 0 75 100 25 50 AMBIENT TEMPERATURE (C)
125
1046 G10
1046 G11
V + (5V) IS
3 4
RL
IL VOUT C2 10F
1046 F01
U
UO
V2
LTC1046
APPLICATI
I= V1 - V 2
S I FOR ATIO
Rewriting in terms of voltage and impedance equivalence,
(1 / fC1)
=
V1 - V 2 . REQUIV
A new variable, REQUIV, has been defined such that REQUIV = 1/fC1. Thus, the equivalent circuit for the switched capacitor network is as shown in Figure 3.
REQUIV V1 C2 REQUIV = 1 fC1 RL V2
1046 F03
Figure 3. Switched Capacitor Equivalent Circuit
Examination of Figure 4 shows that the LTC1046 has the same switching action as the basic switched capacitor building block. With the addition of finite switch ON resistance and output voltage ripple, the simple theory, although not exact, provides an intuitive feel for how the device works.
V+ (8) BOOST 3x (1) OSC OSC (7) +2 CAP - (4) VOUT (5) C2 LV (6)
SW1 CAP + (2)
SW2
+
C1
CLOSED WHEN V + > 3.0V
GND (3)
1046 F04
Figure 4. LTC1046 Switched Capacitor Voltage Converter Block Diagram
For example, if you examine power conversion efficiency as a function of frequency (see typical curve), this simple theory will explain how the LTC1046 behaves. The loss, and hence the efficiency, is set by the output impedance.
+
U
As frequency is decreased, the output impedance will eventually be dominated by the 1/fC1 term and power efficiency will drop. The typical curves for power efficiency versus frequency show this effect for various capacitor values. Note also that power efficiency decreases as frequency goes up. This is caused by internal switching losses which occur due to some finite charge being lost on each switching cycle. This charge loss per unit cycle, when multiplied by the switching frequency, becomes a current loss. At high frequency this loss becomes significant and the power efficiency starts to decrease. LV (Pin 6) The internal logic of the LTC1046 runs between V+ and LV (Pin 6). For V+ greater than or equal to 3V, an internal switch shorts LV to GND (Pin 3). For V+ less than 3V, the LV pin should be tied to ground. For V+ greater than or equal to 3V, the LV pin can be tied to ground or left floating. OSC (Pin 7) and BOOST (Pin 1) The switching frequency can be raised, lowered or driven from an external source. Figure 5 shows a functional diagram of the oscillator circuit.
V+ 2I BOOST (1) I OSC (7) 14pF 2I LV (6) I
1046 F05
W
U
UO
SCHMITT TRIGGER
Figure 5. Oscillator
5
LTC1046
APPLICATI S I FOR ATIO
By connecting the BOOST (Pin 1) to V+, the charge and discharge current is increased and, hence, the frequency is increased by approximately three times. Increasing the frequency will decrease output impedance and ripple for higher load currents. Loading Pin 7 with more capacitance will lower the frequency. Using the BOOST pin in conjunction with external capacitance on Pin 7 allows user selection of the frequency over a wide range. Driving the LTC1046 from an external frequency source can be easily achieved by driving Pin 7 and leaving the BOOST pin open, as shown in Figure 6. The output current from Pin 7 is small, typically 15A, so a logic gate is capable of driving this current. The choice of using a CMOS logic gate is best because it can operate over a wide supply voltage range (3V to 15V) and has enough voltage swing to drive the internal Schmitt trigger shown in Figure 5. For 5V applications, a TTL logic gate can be used by simply adding an external pull-up resistor (see Figure 6). Capacitor Selection While the exact values of CIN and COUT are noncritical, good quality, low ESR capacitors such as solid tantalum
REQUIRED FOR TTL LOGIC LTC1046 NC 1 2 BOOST CAP + GND CAP - V+ OSC LV VOUT 8 7 6 5 C2
-(V +)
+
C1
3 4
Figure 6. External Clocking
6
+
U
are necessary to minimize voltage losses at high currents. For CIN the effect of the ESR of the capacitor will be multiplied by four, due to the fact that switch currents are approximately two times higher than output current, and losses will occur on both the charge and discharge cycle. This means that using a capacitor with 1 of ESR for CIN will have the same effect as increasing the output impedance of the LTC1046 by 4. This represents a significant increase in the voltage losses. For COUT the effect of ESR is less dramatic. COUT is alternately charged and discharged at a current approximately equal to the output current, and the ESR of the capacitor will cause a step function to occur, in the output ripple, at the switch transitions. This step function will degrade the output regulation for changes in output load current, and should be avoided. Realizing that large value tantalum capacitors can be expensive, a technique that can be used is to parallel a smaller tantalum capacitor with a large aluminum electrolytic capacitor to gain both low ESR and reasonable cost. Where physical size is a concern some of the newer chip type surface mount tantalum capacitors can be used. These capacitors are normally rated at working voltages in the 10V to 20V range and exhibit very low ESR (in the range of 0.1).
V+ 100k OSC INPUT
1046 F06
W
U
UO
LTC1046
TYPICAL APPLICATI
Negative Voltage Converter
Figure 7 shows a typical connection which will provide a negative supply from an available positive supply. This circuit operates over full temperature and power supply ranges without the need of any external diodes. The LV pin (Pin 6) is shown grounded, but for V+ 3V, it may be floated, since LV is internally switched to GND (Pin 3) for V+ 3V. The output voltage (Pin 5) characteristics of the circuit are those of a nearly ideal voltage source in series with an 27 resistor. The 27 output impedance is composed of two terms: 1) the equivalent switched capacitor resistance (see Theory of Operation), and 2) a term related to the ON resistance of the MOS switches. At an oscillator frequency of 30kHz and C1 = 10F, the first term is:
REQUIV =
(fOSC / 2) * C1
1
=
Figure 8. Voltage Doubler
1 = 6.7. 15 * 103 * 10 * 10 -6
Notice that the equation for REQUIV is not a capacitive reactance equation (XC = 1/C) and does not contain a 2 term. The exact expression for output impedance is complex, but the dominant effect of the capacitor is clearly shown on
LTC1046 1 2 BOOST CAP + GND CAP - V+ OSC LV VOUT 8 7 6 5 10F TMIN TA TMAX V+ 1.5V TO 6V REQUIRED FOR V + < 3V VOUT = -V +
+
10F
3 4
Figure 7. Negative Voltage Converter
+
UO
S
the typical curves of output impedance and power efficiency versus frequency. For C1 = C2 = 10F, the output impedance goes from 27 at fOSC = 30kHz to 225 at fOSC = 1kHz. As the 1/fC term becomes large compared to switch ON resistance term, the output resistance is determined by 1/fC only. Voltage Doubling Figure 8 shows a two diode, capacitive voltage doubler. With a 5V input, the output is 9.1V with no load and 8.2V with a 10mA load.
LTC1046 1 2 3 4 BOOST CAP + GND CAP - V+ OSC LV VOUT 8 7 6 5 V+ 1.5V TO 6V
+
VD REQUIRED FOR V + < 3V
+
VD
VOUT = 2 (VIN - 1)
+
10F
+
10F
1046 F08
Ultraprecision Voltage Divider An ultraprecision voltage divider is shown in Figure 9. To achieve the 0.0002% accuracy indicated, the load current should be kept below 100nA. However, with a slight loss in accuracy, the load current can be increased.
LTC1046 1 2 BOOST CAP + GND CAP - V+ OSC LV VOUT 8 7 6 5
1046 F09
V+ 3V TO 12V
+ C1
10F V+ 0.002% 2 TMIN TA TMAX IL 100nA
3 4
+
C2 10F
REQUIRED FOR V + < 6V
1046 F07
Figure 9. Ultraprecision Voltage Divider
7
LTC1046
TYPICAL APPLICATI
Battery Splitter A common need in many systems is to obtain positive and negative supplies from a single battery or single power supply system. Where current requirements are small, the circuit shown in Figure 10 is a simple solution. It provides symmetrical positive or negative output voltages, both
LTC1046 1 VB 9V C1 10F 2 BOOST CAP + GND CAP - V+ OSC LV VOUT 8 7 6 5 +VB /2 4.5V REQUIRED FOR VB < 6V -VB /2 -4.5V C2 10F OUTPUT COMM0N
+
3 4
3V VB 12V
Figure 10. Battery Splitter
1 2 C1 10F
BOOST CAP + GND CAP -
+
3 4
OPTIONAL SYNCHRONIZATION CIRCUIT TO MINIMIZE RIPPLE
Figure 11. Paralleling for 100mA Load Current
V+ LTC1046 1 2 BOOST CAP + GND CAP - 8 V+ OSC LV VOUT 7 6 5 -(V +) 10F C1 10F
FOR VOUT = -3V + LTC1046 1 2 3 4 BOOST CAP + GND CAP - V+ OSC LV VOUT 8 7 6 5
FOR VOUT = -2V +
+
10F
3 4
VOUT 10F
1046 F12
Figure 12. Stacking for Higher Voltage
8
+
+
+
+
UO
S
equal to one half the input voltage. The output voltages are both referenced to Pin 3 (output common). If the input voltage between Pin 8 and Pin 5 is less than 6V, Pin 6 should also be connected to Pin 3, as shown by the dashed line. Paralleling for Lower Output Resistance Additional flexibility of the LTC1046 is shown in Figures 11 and 12. Figure 11 shows two LTC1046s connected in parallel to provide a lower effective output resistance. If, however, the output resistance is dominated by 1/fC1, increasing the capacitor size (C1) or increasing the frequency will be of more benefit than the paralleling circuit shown. Figure 12 makes use of "stacking" two LTC1046s to provide even higher voltages. In Figure 12, a negative voltage doubler or tripler can be achieved depending upon how Pin 8 of the second LTC1046 is connected, as shown schematically by the switch.
V+ LTC1046 V+ OSC LV VOUT 8 7 6 5 C1 10F 1 2 LTC1046 BOOST CAP + GND CAP - V+ OSC LV VOUT 8 7 6 5 VOUT = -(V +) C2 20F
1046 F10
+
3 4
1/4 CD4077
1046 F11
+
LTC1046
PACKAGE DESCRIPTIO U
Dimensions in inches (milimeters) unless otherwise noted.
J8 Package 8-Lead CERDIP (Narrow 0.300, Hermetic)
(LTC DWG # 05-08-1110)
CORNER LEADS OPTION (4 PLCS)
0.005 (0.127) MIN
0.405 (10.287) MAX 8 7 6 5
0.023 - 0.045 (0.584 - 1.143) HALF LEAD OPTION 0.045 - 0.068 (1.143 - 1.727) FULL LEAD OPTION 0.300 BSC (0.762 BSC)
0.025 (0.635) RAD TYP 1 2 3
0.220 - 0.310 (5.588 - 7.874)
4
0.200 (5.080) MAX 0.015 - 0.060 (0.381 - 1.524)
0.008 - 0.018 (0.203 - 0.457)
0 - 15
NOTE: LEAD DIMENSIONS APPLY TO SOLDER DIP/PLATE OR TIN PLATE LEADS
0.045 - 0.065 (1.143 - 1.651) 0.014 - 0.026 (0.360 - 0.660) 0.100 (2.54) BSC
0.125 3.175 MIN
J8 1298
9
LTC1046
PACKAGE DESCRIPTIO U
Dimensions in inches (milimeters) unless otherwise noted.
N8 Package 8-Lead PDIP (Narrow 0.300)
(LTC DWG # 05-08-1510)
0.400* (10.160) MAX 8 7 6 5
0.255 0.015* (6.477 0.381)
1 0.300 - 0.325 (7.620 - 8.255)
2
3
4 0.130 0.005 (3.302 0.127)
0.045 - 0.065 (1.143 - 1.651)
0.009 - 0.015 (0.229 - 0.381)
0.065 (1.651) TYP 0.125 (3.175) 0.020 MIN (0.508) MIN 0.018 0.003 (0.457 0.076)
N8 1098
(
+0.035 0.325 -0.015 8.255 +0.889 -0.381
)
0.100 (2.54) BSC
*THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.010 INCH (0.254mm)
10
LTC1046
PACKAGE DESCRIPTIO
0.010 - 0.020 x 45 (0.254 - 0.508) 0.008 - 0.010 (0.203 - 0.254) 0- 8 TYP
0.014 - 0.019 (0.355 - 0.483) TYP *DIMENSION DOES NOT INCLUDE MOLD FLASH. MOLD FLASH SHALL NOT EXCEED 0.006" (0.152mm) PER SIDE **DIMENSION DOES NOT INCLUDE INTERLEAD FLASH. INTERLEAD FLASH SHALL NOT EXCEED 0.010" (0.254mm) PER SIDE
0.016 - 0.050 (0.406 - 1.270)
Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
U
Dimensions in inches (milimeters) unless otherwise noted.
S8 Package 8-Lead Plastic Small Outline (Narrow 0.150)
(LTC DWG # 05-08-1610)
0.189 - 0.197* (4.801 - 5.004) 8 7 6 5
0.228 - 0.244 (5.791 - 6.197)
0.150 - 0.157** (3.810 - 3.988)
1
2
3
4
0.053 - 0.069 (1.346 - 1.752)
0.004 - 0.010 (0.101 - 0.254)
0.050 (1.270) BSC
SO8 1298
11
LTC1046 RELATED PARTS
PART NUMBER LTC1044A LT(R)1054 LTC1550 LT1611 LT1617 LTC1754-5 DESCRIPTION 12V CMOS Voltage Converter Switched Capacitor Voltage Converter with Regulator Low Noise, Switched Capacitor Regulated Inverter 1.4MHz Inverting Switching Regulator Micropower Inverting Switching Regulator Micropower Regulated 5V Charge Pump in SOT-23 COMMENTS Doubler or Inverter, 20mA IOUT, 1.5V to 12V Input Range Doubler or Inverter, 100mA IOUT, SO-8 Package < 1mVP-P Output Ripple, 900kHz Operation, SO-8 Package 5V to -5V at 150mA, Low Output Noise, SOT-23 Package 5V to - 5V at 20A Supply Current, SOT-23 Package 5V/50mA, 13A Supply Current, 2.7V to 5.5V Input Range
12
Linear Technology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408)432-1900 q FAX: (408) 434-0507 q www.linear-tech.com
1046fa LT/TP 1099 2K REV A * PRINTED IN USA
(c) LINEAR TECHNOLOGY CORPORATION 1991

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